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外文翻译参考
外文翻译
毕业设计题目:
GPS抗干扰天线技术—多频带高增益微带天线单元的仿真与设计
原文1:
H-MRTDsimulationofdual-frequencyminiaturepatchantenna
译文1:
双频微型贴片天线的H-MRTD模拟
原文2:
ANovelMethodforDesigningDual-FrequencySlotPatchAntennaswithTwoPolarizations
译文2:
新的双频双极化开槽微带天线的设计方法
H-MRTDsimulationofdual-frequencyminiaturepatchantenna
YUWen-ge1,2,ZHONGXian-xin1,LIXiao-yi1,CHENShuai1
(1.TheKeyLabforOptoelectronicTechnology&SystemsofMinistryofEducation,
ChongqingUniversity,Chongqing400044,China;
2.BasicLogisticalEngineeringUniversity,Chongqing400016,China)
Abstract:
AnovelMEMSdual-bandpatchantennaisdesignedusingslot-loadedandshort-circuitedsize-reductiontechniques.Bycontrollingtheshort-planewidth,f10andf30,tworesonantfrequencies,canbesignificantlyreducedandthefrequencyradio(f30/f10)istunableintherange1.7~2.3.TheHaar-Wavelet-Basedmultiresolutiontimedomain(H-MRTD)isusedformodelingandanalyzingtheantennaforthefirsttime.Inaddition,themathematicalformulaeareextendedtoaninhomogenousmedia.Numericalsimulationresultsarecomparedtothoseachievedusingtheconventional3-Dfinite-differencetime-domain(FDTD)methodandmeasured.Ithasbeendemonstratedthat,withthistechnique,spacediscretizationwithonlyafewcellsperwavelengthgivesaccurateresults,leadingtoareductionofbothmemoryrequirementsandcomputationtime.
Keywords:
dual-frequencyantenna;H-MRTDmethod;FDTDmethod;MEMS;UPMLabsorbingboundaryconditions
1 Introduction1
Recently,patchantennaresearchhasfocusedonreducingthesizeofthepatch,whichisimportantinmanycommercialandmilitaryapplications.IthasbeenshownthattheresonantfrequencyofamicrostripantennacanbesignificantlyreducedbyintroducingaShort-circuitedplaneorapartlyshort-circuitedplanewheretheelectricfieldoftheresonantmodeiszero[1-3],orashort-pinnearthefeedprobe[4].Usingtwostackedshort-circuitedpatches,dual-frequencyoperationhasbeenobtained[5].However,theuseofastackedgeometryleadstoincreasesinthethicknessandcomplexityofthepatch.Inthispaper,wedemonstratethatbyshort-circuitingthezeropotentialplaneofaslottedpatchexcitedwithadominantmode(TM10),theresonantfrequencies,f10andf30,ofthetwooperatingmodescanbeapproximatelyhalvedandcanevenbesignificantlyreducedbydecreasingtheshorted-planewidth.Thisindicatesthatalargereductioninantennasizecanbeobtainedbyusingtheproposeddesign,ascomparedtothatofaregularslot-loadedpatch.
Thefinite-differencetime-domain(FDTD)method[6]iswidelyusedforsolvingproblemsrelatedtoelectromagnetism.However,therestillexistmanyrestrictivefactors,suchasmemoryshortageandCPUtime,etc.wefirstadoptedthemethodoftheHaar-Wavelet-BasedMultiresolutionTimeDomain(H-MRTD)[7-9]withcompactlysupportedscalingfunctionforafullthree-dimensional(3-D)wavetoYee’sstaggeredcelltoanalyzeandsimulatethedualfrequencymicrostripantenna.ThemajoradvantageoftheMRTDalgorithmsistheircapabilitytodevelopreal-timetimeandspaceadaptivegridsthroughtheefficientthresholdingofthewaveletcoefficients.Usingthistechnique,spacediscretizationwithonlyafewcellsperwavelengthgivesaccurateresults,leadingtoareductionofbothmemoryrequirementandcomputationtime.Associatedwithpracticalmodel,auniaxialperfectlymatchedlayer(UPML)absorbingboundaryconditions[10]wasdeveloped,athree-dimensionalformulationofthediscretedifferenceequationsarisingfromtheMaxwell’ssystemisfirstextendedtoaninhomogenousmedium,itisappliedtotheanalysisofdual-frequencyminiaturepatchantenna.
2 Dual-frequencyslot-loadedpatchantenna
2.1 Designofslot-loadedpatchantenna
Thelayoutoftheslot-loadedpatchantennadesignedinthispaperisshowninFig.1.AsingleslotwithdimensionsL×Wiscutinarectangularpatchwithdimensionsa×bwithashort-circuitedplaneofwidthplacedatitsotherside.Theparametersoftheantennaarea=38mm,b=25mm,L=36mm,W=1mm,d=2mm,h=3mm,r=1mm,respectively.OwingtobeingcompatiblewithstandardICtechnology,andpronetointegrationwithothercomponents,siliconwafer(εr=11.7)wasselectedasalayerofmicrostripsubstrate.Betweenthegroundplateandthewaferthereisalayeroffoam(εr=1.07),whichcouldsuppresssurfacewaveinducedinthewafersubstrate,asaresult,theefficiencyandthebandwidthoftheantennawereincreased,andtheradiationpatternimproved.
Fig.1Geometryofdual-bandslot-loadedmicrostripantenna
2.2 Measuredresults
Theparametersoftheslotantennaareselectedasabovementioned.ThemeasurementscarriedoutonanAgilent8720Cvectornetworkanalyzer.Itisthenfoundthat,bycontrollingtheshorted-planewidth,boththeTM10andTM30modesarestronglyperturbed.Fig.2showstypicalresultsofthemeasuredreturnlossforthecaseswiths/a=1,0.25,and0.1.RegardingtheresultsshowninFig.2,itcanbeseenthattheperturbedTM10andTM30modesareexcitedwithgoodimpedancematching.However,whens/a<0.1,therenofeedpointcanbefoundforexcitingthetwofrequencieswithgoodimpedancematching.Thisindicatesthattherearelimitationstothepresentdual-banddesign.Itcanbeseenthattheobtainedfrequencyratio(f30/f10)ofthetwofrequenciesforpresentdesignvariesintherange1.7~2.3.Ontheotherhand,forthecases/a=0.1,showninFig.2,thefrequencyf10occurringat1.562GHzis~0.31timesthat(5.038GHz)foraregularhalf-wavelengthpatchwiththesamepatchsize.Inotherwords,thesizeofthedesignedantennainthispaperismuchsmallerthanregularhalf-wavelengthpatchantenna.
Fig.2Measuredreturnlossfordifferentshorted-planewidths
3 3-DH-MRTDalgorithm
3.1 Numericalformulationsofthe3-DH-MRTDmethod
Maxwell’scurlequationsinanisotropicmedium:
(1)
whereεispermittivity,μispermeability,σiselectricconductivity.Eachfieldcomponentisexpandedintoscalingfunctions:
(2)
Andwavelets:
(3)
Where,
and
.
Expansionandtestingisperformedforeachspatialcoordinates={x,y,z}withcorrespondingdiscretizationindicesu={k,l,m},aswellasfortimewithrectangularpulsehn(t).Incompactnotations,thex-directedelectricfieldcomponentinthestaggeredYee’sgridofsizeΔx,Δy,Δzisrepresentedas
(4)
wherex=kΔx,y=lΔy,z=mΔz,t=nΔt.
Thesummationoverξηζincludeseighttermsstemmingfromallthepermutationsofscalingfunctionsandwavelets:
.TherepresentationoftheotherfieldcomponentsiseasilyderivedthroughpermutationoftheindicesandfollowsthesameruleasforstandardFDTDscheme.InsertingtheaboveexpressionsintothedifferenceequationandperformingaGalerkintestprocedure[12]leadstothefollowingexpressionsfortheelectricfieldwithineachcell{k,l,m}:
(5)
where{0,1,2,3}denotes,respectively,{u,u+1/2,u-1/2,u+1}foreachu={k,l,m,n}.Informula(5),therearethreedifferentΕxvalueswithinonetimestep,thisbringsaboutinconvenienceforprogramdesign.Inordertoavoidtheshortcoming,wecanadoptapproximationasfollows:
(6)
Similarexpressionsareobtainedfortheotherfieldcomponents.
3.2 Absorbingboundarycondition
Thefieldcomputationdomainmustbelimitedinsizebecausethecomputercannotstoreanunlimitedamountofdata.Thecomputationdomainmustbelargeenoughtoenclosethestructureofinterest.Inthispaper,weadopteduniaxialperfectlymatchedlayer(UPML)absorbingboundaryconditions.Consideronedimensionwaveequationpropagatedalong+zdirection:
,(7)
whereσ′=σ/ε,visthephasevelocityintheconcernedvolume.Becausetheconductivityσisprojectedincomputationdomain,itwillresultinnumericdispersionifweusedirectlydiscreteapproximationforformula(7),Let
,then
itsfinitedifferenceformis
(9)
Thedifferenceformofformula(7)is
where
aretheMRTDcoefficients.
TheUPMLmaterialparametersarechosentobe
fortheinnercomputationregion.ThemaximumvalueofσattheendoftheUPMLregionischosentobe
where⊿isthecelldimensionperpendiculartotheUMPLinterfacetotheregularregion.TheUMPLregionisbackedbyaperfectelectricconductorwallimplementedusingthemirrorprinciple.
4 Computedresults
Inmicrowavecircuitanalysis,Gaussimpulseisgenerallyselectedasanexcitationforsmoothnessintimedomainandeasyspectrumwidthsetting.ThewidthofGausspulseisT=18ps,assumethatthetimedelayt0=3T=54ps,TheresponsevalueofthefrequencydomaincanbecalculatedbyFouriertransformingthetimedomainvalue.
ThecirclewavelossesoftheantennacomputedareshowninFig.3andFig.4fors/a=1ands/a=0.25,respectively.Thecomputedcurvesbasedcomputationdomain100×120×60andΔx=Δy=0.15mm,Δz=0.015mm.FromFig.3andFig.4,wecanfindthecomputedresultsbyusingFDTDmethod,andH-MRTDmethodareingoodagreementwithmeasuredresults.ThedriftsbetweenthemensuredvalueandthecomputedvaluebyusingFDTDandH-MRTDareabout2%and2.5%infine-grid,respectively.Thelengthofthenovelpatchantennaislessthan1/7wavelength,theefficiencythisnovelantennaarriveat70%.Thecharacteristicparameterssuchaseffectivedielectricconstant,thecharacteristicimpedanceinspectrumdomaincouldbeworkedoutbyFouriertransform.
Fig.3Computedreturnlossfors/a=1
Fig.4Computedreturnlossfors/a=0.25
ThesesimulationswereperformedbyXFDTD,theinformationaboutdual-frequencyantennasimulati